 Open Access
 Authors : Khalid Ateea Alfaitori , Haytham Yousef Mustfa , Saad. M. Saad , Naser El Naily
 Paper ID : IJERTV10IS030286
 Volume & Issue : Volume 10, Issue 03 (March 2021)
 Published (First Online): 22042021
 ISSN (Online) : 22780181
 Publisher Name : IJERT
 License: This work is licensed under a Creative Commons Attribution 4.0 International License
Mathematical Model and Sensitivity Analysis of a Parallel 3Phase Voltage Source Inverter
Khalid Ateea Alfaitori
Electronics & Communication Technology Department College of Electrical and Electronics TechnologyBenghazi
Haytham Yousef Mustfa
Electrical System Technology Department
College of Electrical and Electronics TechnologyBenghazi
Saad. M. Saad
College of Electrical and Electronics TechnologyBenghazi
Naser El Naily
College of Electrical and Electronics TechnologyBenghazi
AbstractRecently, there has been a great interest in grid connected renewable energy resources such as photovoltaic, fuel cells and wind energy. Typically, parallelconnected three phase voltage source inverters are utilized in these grid connected renewable energy applications. In this paper, modeling and control of a parallel three phase voltage source inverter is considered. To set the stage, the inverter model is derived by defining the variations in the output dq voltages and dq currents as the system states. The variation in duty cycle is defined as the control input. The system control is implemented using two different control strategies, i.e., (voltage control mode of the first inverter and power control mode of the second inverter). To optimize the system performance, the sensitivity analysis is applied to the inverter model. To verify the eigenvalue analysis, timedomain simulation is used to determine the effects of controller and parameter variations on the system stability.
KeyWords: Parallel inverter; sensitivity analysis; eigenvalue location; SVPWM

INTRODUCTION
The surge of applications of power electronics in industrial, commercial, military, aerospace, and residential areas has driven many research studies in this subject [1]. The objective of these studies is mainly to obtain, highly reliable and efficient power electronic components with low cost and compact size. In addition, power electronics play an important role in the advancement of distributed energy resources [1]. Due to their environmental and economic benefits compared to large power plants, the reliance on distributed power sources, such as fuel cells, wind turbines and photovoltaic systems has increased in the recent years. However, these sources do not necessarily generate the desired rated voltage and frequency. Therefore, a voltage source inverter (VSI) is required to be used as an interface between the distributed energy source and the main grid as shown in Fig. 1. Distributed power sources in microgrid can operate in parallel to the grid or in the islanded mode [2]. Consequently, many research has focused recently on the use of a set of inverters connected in parallel.
Parallel connected inverters enable the load current to be shared among different distributed resources and the main grid. As a result, the reliability of the whole power generation system will be improved. Due to the existence of large number of power converters, the stability problem becomes increasingly important in distributed energy systems. To improve the stability and the performance of the distributed energy resource,
smallsignal modeling of the parallel voltage source inverter system is considered [2], [3].
There are many research papers provide an extended review for control techniques of parallel inverters, [4][6]. The control strategies may be classified as centralized and decentralized control strategies [4]. The centralized control strategy has many good advantages. For instance, the current sharing is forced at all times even during transient, and different power rating inverters can be connected without changing the control structure. The system may also be easily maintained and replaced. However, this strategy has a few serious disadvantages. One of the major disadvantages is due to the reference voltage and current signals that have to be sent to all inverters in the network. This requires a high bandwidth communication link in the system which is sensitive to nonlinear loads. On the other hand, Master/Slave control method gives a good load sharing and synchronization. The main disadvantage of the master/slave method is that it is not redundant since it has a single point of failure.
Furthermore, there are excellent features of the current/power sharing control technique; they have a load sharing with a very good transient response and less circulating current between the inverters. This technique has some problems such as, it is not easily expendable and it requires an interconnection which make the system less reliable. The distributed control strategy, on the other hand, is based on the rotational reference frame rather than stationary reference frame. A current sharing in the system is provided in steady state and during transient. Lower communication bandwidth is needed. However, this strategy is not appropriate for unbalanced systems. Droop control method has many desirable features such as expandability, modularity, redundancy, and flexibility. There are as well some drawbacks such as, slow transient response and possibility of circulating current. These reviews lead to the control techniques of parallel inverter which are classified according to mode of operation, and these techniques still require development to overcome some challenges. For instance, a sensitivity analysis should be carried out to achieve system stability.
In this paper, a general control system model with two different control modes of parallel operated inverters are discussed. The average model of the parallel operated voltage source inverters is based on a phase leg and small signal model.
Then the performance of parallel connected voltage source
2
2
0 0 0
2
[2] = 1 [
]
1 [ ] 1 [ 0 ] [ 0 0] . [2] (5)
inverter with voltage control strategy of first inverter and power control strategy of second inverter and frequency domain
2
2
2
2
2
2
2 3
0 0 0
2
1
2
0 0
analysis are validated by timedomain simulation.
[ ] = 1 [1] + 1 [2] 1 [ ] [ 0 0] . [ ] (6)
The organization of this paper will be as follows: the full
2
1
2
2
0 0 0
model of the two parallelconnected three phase voltage source
The model can be simplified based on
=
=
0.
inverters is derived in Section II. In Section III the control
strategies and the closed loop system are considered. Section
The linearization of the largesignal time
aver
1
age m
2
odel around
IV discusses the eigenvalue Loci and sensitivity analysis. Finally, the study presented in this paper is concluded in
the operating point is based on assuming that the input DC power sources are ideal, thus,
1 0 1
1 0 1
Section V.
1
1 1
1
0
1
[ ] = [ [ ] = [1 1
1
] 1 [ ] [ ] . [ ] (7)
[ ] = [ [ ] = [ 
MATHEMATICAL MODEL OF 3PHASE VSIS
2
1 2
1
0
2
CONNECTED IN PARALLEL
2 2
2
] 2 [ ] [ ] . [ ] (8)
2 0 2
2 0 2
The average smallsignal models of the parallel threephase
1
voltage source inverter are presented in this section. The
[ ] = 1 ([ 1] + [ 2]) [
] . [ ] (9)
switching network averaging is performed on a phaseleg basis.
2
1
2
1
After the phaseleg averaging, the average model of a three phase voltage source inverter may be easily established by connecting three averaged phase legs [1], [7].The typical circuit of two parallel threephase voltage source inverters with different DC sources is shown in Fig. 1.
From the average model of parallel VSI the statespace equations can be derived and which will be as follows:
Now, the state space equation of the smallsignal model of parallel voltage source inverters May be achieved. The state variables are defined as [ 1 12 2] and the output variables are [1122] which represent the control variables.
= + (10)
= (11)
1
1
where, is the state variables matrix and is the output matrix
[1] = 1 [
]
1 [
] 1 [ ] (1)
then:
1
1
1
1
1
= [
] (12)
1
1
1 1 2 2
2
2
= [1122] (13)
[2] = 1 [
]
1 [
] 1 [ ] (2)
2
2
2
2
2
2
2
= (14)
Therefore, the state space equations can be obtained and the
1
2
[
] = 1 [1] + 1 [2] 1 [
] (3)
state and input matrices may be respectively expressed as:
2
1
2
2
1
1
2
0 1 0
2
ip1
1 0 1
0 1
2
2
Vdc1
Sap1 Sbp1 Scp1
Va1
Vb1
Vc1
ia1 L1
ib1 VA
ic1 VB
V
1
= 1
0
0 0 0 0
1
0 0 0
(15)
C
San1 Sbn1 Scn1
1
1 0 0 0 0
in1
2C R/2
2
0 1
0 0 0
Ref
ip2
VN [
2 ]
Sap2 Sbp2 Scp2
0 0 0 0
0 0 0 0
Vdc2
Va2
Vb2
Vc2
ia2 L2
ib2 ic2
1
1
0 0 0
San2 Sbn2 Scn2
= 0 1 0 0
(16)
1
2
Ref
in2
0 0
0
2
Fig. 1: Circuit schematic of parallel threephase inverters
0 0 0 2
]
]
[
[2
To linearize the system to design controllers, the model in the stationary coordinates is usually transformed into rotating coordinates. Then, one can obtain the average model of the parallel voltage source inverters in the rotating coordinates:

CONTROL STRATEGY AND CLOSED LOOP SYSTEM
The control scheme of each inverter consists of two cascaded control loops. The inner control loops independently regulate
1
1
0 0 0
1
the inverter output current in the rotating reference frame, id and
[1] = 1 [
]
1 [ ] 1 [ 0 ] [ 0 0] . [1] (4)
1
1
1
1
1
1
1 3
0 0 0
1
iq. The outer loops in the voltage control mode are used to produce the dq axis current references for the inner loops by regulating the voltage at given reference values. In power control mode, the outer loops are used to regulate the active and
reactive power at a given operating point and provide the current references, idref and iqref, in the rotating reference frame for the inner loops [8], [9].
Voltage control mode is used for the first inverter is depicted in Fig.2. The instantaneous values of the first inverters output
2 = (2)( 2) (23)
2 = (2)( 2) (24)
The duty cycle signals of the second inverter may be given as:
current components in rotating reference frame id1ref and iq1ref are used to control the output voltage.
2
. 2
= (2
2
+ )(
+ )(
2
(25)
2)
22 +
va
2
. 2
= (2
2
+ )(
+ )(
2
2)
+ 22
+ (26)
Vdc1
SVPWM
dq
1/vdc1 1/vdc1
Filter
Kidp1+Kidi1/S
Kidp1+Kidi1/S
++
–
L1
L1
L1
L1
– +
Kvdp+KvIi/S
Kvdp+KvIi/S
id1
iq1
+ –
vdref vqref
vd dq
vq
dq
abc
vb vc
ia1
Load
The dynamic behavior of the two parallelconnected inverters including their controllers may be investigated by using a linearized small signal model of the control loops [7], [9]. Then, according the small signal model of the control loops, the duty cycles of the two inverters operated in parallel
Kiqp1+Kiqi1/S
Kiqp1+Kiqi1/S
++ – +
+
+
Kvqp+Kvqi/S
Kvqp+Kvqi/S
– abc
ib1 ic1
with different DC power sources may be written as:
= 1 [(1 )
Fig. 2: First inverter with voltage control mode
1
1
1
1 1
1 1
The voltage at given references in voltage control mode is
+ 11 + 11 + 1 ] (27)
regulated by the outer loops to produce the dq axis current
= 1 [(1
)
+
references for the inner loops [8]. Therefore, the output of the
1
1
1
1 1
1 1
outer voltage controller is inputted to the inner control loop and thus a proportionalintegral (PI) controller is used. Then:
+11 + 1 1 + 1] (28)
= (
+ ) (
) (17)
= 1 [(1 3
)
3
1
2
2
2 2
2 2
2 2
2 2
= (
+ ) (
) (18)
(3
+
)
(3
+ )
1
2 2
2
2
2
2 2
2
2 2
In order to generate the gate control signals that drive the
+22 + 22 ] (29)
switches of the inverter, the outputs from this inner current
= 1
3
+ (1 3
) +
loops are inputted to the Space Victor Pulse Width Modulation (SVPWM) module [8], [9], [10]. The duty cycles signals are
2
(
[2 2
3
2
2 2
)
+ (3
2 2
2 2
)
given as:
2 2 2
2
2
2 2
2
2
2
1. 1 = (1 +
1) ( 1 1) 1 1 + (19)
+22 + 22] (30)
.
= (
1
) +
+
(20)
The small signal model of controller provides six new state
1
1
1
1
1
1 1
variables, which are: (
1
1
1
1
2
2).
+ ) (
+ ) (
The second inverter is using power control mode. The instantaneous values of the second inverters output curent components id2ref and iq2ref are used to control the output active and reactive power respectively as shown in Fig 3.
In the power control mode, the active and reactive power are
Therefore, the control output can be expressed as:
1
1
= [] + [( ) ] (31)
The complete model of the closed loop system may be expressed as:
controlled at given set points by the outer loops to produce the
[] = (
+ )[] +
[()
] (32)
dq axis current references for inner loops [8]. Where:
3
where
1 1 1
2
2
2
= ( 2 + 2) (21)
= [ 1 1 2 2111122] (33)
= 3 ( ) (22)
Vdc2
2
Filter
2
2
va
vb Load
The order of the overall closed loop system is the twelfths, because there are 12 state variables (N=12). In frequency domain, we can get:
vc () = (
)1.
(34)
SVPWM
+
vd dq
()
1 1 1 2
Kidp2+Kidi2/S
Kidp2+Kidi2/S
+ – +
– P
Kpp2
Kpp2
+ vq
where: () = [(
)
](), A and B are the state and
1/vdc2
id2

ref
abc
1 1
dq 1/v
dc2
L2
L2
Kqp2
Kqp2
iq2

ref
dq ia2
the input matrices of the closed loop system.
L2
L2
Kiqp2+Kiqi2/S
Kiqp2+Kiqi2/S
++ – +
+
+ – Q
abc
ib2 ic2


EIGENVALUE LOCI AND SENSITIVITY ANALYSIS
Fig. 3: Second inverter with power control mode
The outputs of these outer controllers are the inputs to the inner control loops. A proportional (P) controller is adopted. Thus,
The locations of eigenvalues move with controller and system parameters in the frequency domain. The movement of eigenvalues by these parameters leads to unsatisfactory oscillatory response. Various loci of closed loop poles by changing a controller and system parameters are presented in
this section in order to further study the level of eigenvalue sensitivity. All eigenvalues of the system are given in Table I.
TABLE I
Eigenvalues
3.189*105
1.2745*105
1.0695*104 Â± 3.14*103i
125 Â± 9.682*104i
50 Â± 1.118*103i
150.177
4.110*107 Â± 1.21*108i
100.031
Eigenvalues
3.189*105
1.2745*105
1.0695*104 Â± 3.14*103i
125 Â± 9.682*104i
50 Â± 1.118*103i
150.177
4.110*107 Â± 1.21*108i
100.031
THE EIGENVALUES OF PARALLEL INVERTERS SYSTEM
The loci of the eigenvalues which influenced by current controller parameters of first inverter Kidp1 in the frequency domain are shown in Fig. 6.
600
Kidp1=0 Kidp1=1
Kidp1=0.01 Kidp1=100
400
Two real eigenvalues are very close to the origin point are
200
x
96.8 x
influenced by increasing Kvdi from 0 to 4000 as shown in Fig.
0 x x
24998.9 96.8 x
4. When Kvdi is increasing from 0 to 400,one of these real eigenvalues at the origin point and another is very close to the origin point move toward each other and become a pair of complex conjugate poles near to origin point. This results in improvement of damping ratio and increase in system stability.
Imaginary Axis
Imaginary Axis
200
400
600
x
125
x 108
4 3.5
3 2.5
2 1.5 1
0.5 0
0.5 1
2.0
Imaginary Axis
Imaginary Axis
1.5
1.0
0.5
0.0
0.5
Kvdi=0 Kvdi=400 Kvdi=4000
x
x
x x x
x
Real Axis
Fig. 6:The eigenvalues location with an increasing Kidp1
When Kidp1 equals zero, the system is unstable because there are a pair of complex conjugate poles in the right half plane. When it is increased to about 0.01, these eigenvalues move from the right half plan (RHP) to the left half plan (LHP) and continue to move away from the origin point until Kidp1 equals
1.0
1. With Kidp2 increasing from 0 to 0.01, a pair of complex
1.5
5 4.5 4 3.5 3 2.5 2 1.5 1 0.5 0 x 106
conjugate eigenvalues moves from RHP to the LHP, thereby
2.0
Real Axis
the system moves to stable state as shown in Fig. 7. When
Fig. 4:The eigenvalues location with an increasing Kvdi
Then Kvdi is more than 400, these complex eigenvalues become two real poles which are less influenced by Kvdi. Therefore, Kvdi is selected to be 400 or any value more than 400. In Fig. 5, Kvqi is increasing from 0 to 4000, while all other parameters are set to be constant. There are two real eigenvalues influenced by Kvqi. When Kvqi is increasing from 0 to 400 one real pole at origin point moves towards the other real pole that is very close to the origin point and become a pair of complex conjugate poles with more stable because
Kidp2is increased from 0.01 to 1, this pair of complex conjugate eigenvalues becomes a pair of two real eigenvalues with less overshoot and oscillations.
Furthermore, when Kidp2is increased from 1 to 100, one of these real eigenvalues moves quickly towards origin point which reduce the system stability, and another real eigenvalue moves far away from origin point towards LHP. This shows the stability of the system is less sensitive to this eigenvalue. So Kidp2 is set to be 1.
improvement of damping ratio. This pair of complex conjugate eigenvalues with Kvqi more than 400 becomes two real eigenvalues with less sensitivity to the variation of Kvqi. So Kvqi is set to be 400 or any other value more than 400.
x 108
2.0
Kvqi=0
6000
4000
Imaginary Axis
Imaginary Axis
2000
0
x
x x x
3.2*1o7 3.2*1o5
x
Kidp2=0 Kidp2=0.01
Kidp2=1 Kidp2=100
x
1.5
Imaginary Axis
Imaginary Axis
1.0
0.5
Kvqi=400 Kvqi=4000
2000
x
4000
0.0 x
0.5
1.0
1.5
2.0
x x x
x
x
x
6000
250 200 150 100 50 0
Real Axis
Fig. 7:The eigenvalues location with an increasing Kidp2
Fig. 8 shows the loci of eigenvalues which are influenced by
5 4.5 4 3.5 3 2.5 2 1.5 1 0.5 0 x 106
Real Axis
Fig. 5:The eigenvalues location with an increasing Kvqi
filter parameter L. When L is increasing from 4 mH to 100 mH there are two a pair of complex conjugate eigenvalues moves quickly towards origin point and two real poles move toward
imaginary axis horizontally on the real axis. This leads to a decrease in system stability.
150
L=4 mH

CONCLUSION
In this paper, control strategies of two inverters operated in parallel were considered. The control strategy of the first inverter was based on the voltage control mode while the power
100
Imaginary Axis
Imaginary Axis
50
x
0 x x x x
x L=10 mH
x L=50 mH
x L=100 mH
x
control mode was used for the second inverter. Herein, two different DC sources were modeled based on an averaged model of the inverter. Using MATLAB/SIMULINK
1.27*105
0
0.5*105
1.1*104
xx
0.5*104 x
x
x
x
simulation, the performances of these strategies is evaluated. The eigenvalue analysis of the smallsgnal model which is based on the averaged model was also verified by the
0 x
0 x
x
x
x
x
50
xxx
simulation results. The simulation results were also used to
100
150
3.18*105
1.27*105
2.54*104 1.26*104 x
x x
x
determine the effects of the controller and system parameter variations on the system stability. By recognizing the control and filter parameters that achieve the best response of the system, designers would be capable of improving the
400 350 300 250 200 150 100 50 0 50 100
Real Axis
Fig. 8:The eigenvalues location with an increasing L
The reference value of the three phase output voltages peak is set to be 170V. Initially the active and reactive power of the second inverter are 10KW and 2KVAR respectively. These values are reduced by 50% after 0.35 seconds. The reference frequency is set to be 50 Hz. The simulation is run for 0.5 seconds and results under two different control strategies which are carried out and used to verify the eigenvalue analysis.
The timedomain simulation with L variation is shown in Fig. 9. When L is set as 4 mH the active power of the second inverter converges to high stable state with small oscillation compared to the two other values. From these simulation results, the system has large oscillation when this parameter is decreased to 0.63 mH. The stability of the system is reduced with high overshoot when L equals 10 mH. This is almost consistent with the frequencydomain analysis.
—— L=4 mH
—— L=10 mH
—— L=0.63 mH
—— L=4 mH
—— L=10 mH
—— L=0.63 mH
18000
16000
Active PowerP (W)
Active PowerP (W)
14000
12000
10000
8000
6000
4000
2000
0
2000
0 0.05 0.1 0.15 0.2 0.25 0.3 0.35 0.4 0.45 0.5
t (s)
Fig. 9:Output active power of second inverter with an increasing L
performance of the system.
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