 Open Access
 Total Downloads : 751
 Authors : Mr. B. Suresh, Dr. G. Saravanakumar, Mr. R. Sampath Kumar
 Paper ID : IJERTV2IS3362
 Volume & Issue : Volume 02, Issue 03 (March 2013)
 Published (First Online): 21032013
 ISSN (Online) : 22780181
 Publisher Name : IJERT
 License: This work is licensed under a Creative Commons Attribution 4.0 International License
Balancing The Capacitor Voltage in NPCAPF using Pulse width Modulation Control
Mr. B. SURESH,1 
Dr. G. SARAVANAKUMAR,2 
Mr. R. SAMPATH KUMAR,3 
Assistant Professor, 
Professor & Head, 
Assistant Professor, 
Dept. of Electrical Engg., 
Dept. of EIE, 
Dept. of Electrical Engg., 
Angel College of Engg. & Tech., 
Tamilnadu College of Engg,, 
Angel College of Engg. & Tech., 
Tirupur 641 665. 
Coimbatore. 
Tirupur 641 665. , 
Tamil Nadu, INDIA. 
Tamil Nadu, INDIA. 
Tamil Nadu, INDIA. 
Abstract The Neutral Point Clamped (NPC) voltage source inverter (VSI), without a separately supporting dc link is used to maintain the two dclink capacitor voltages in a balanced condition. In this paper, balancing of the capacitor voltages for these two capacitor voltage source possibilities are determined and pulse width modulation technique is proposed to independently balance the capacitor voltages. This technique considers the average energy effect of each capacitor voltages. The technique minimizes the voltage rating overheads of the hardware, reduces the voltage ripple and attenuates the negative effects associated with dclink voltage oscillations. It increases the power handling capability and reduces voltage and current harmonics. The proposed scheme was simulated by using MATLAB Simulink.
Index Terms DClink voltage ripple, Neutral Point diode Clamped (NPC), Pulse Width Modulation (PWM).

INTRODUCTION
The Neutral Point Diode Clamped (NPC) voltage source inverter (VSI) is a common structure in medium and high power industrial applications. It avoids the complexity associated with the series connection of semiconductor switches. It causes a low voltage stress on semiconductor switches thus increasing the power handling capability and produces lower current / voltage harmonics.
One threelevel NPC inverter is used to balance the voltages of the two series connected capacitors across the dc link. The threelevel NPC VSI structure without an external dc supply is shown in Fig. 1. This voltage oscillation causes adverse effects, such as low frequency harmonics in the output linetoline voltages, the bridge devices and capacitors must withstand higher varying voltage stresses. Methods to eliminate the voltage ripple have been proposed both with Sinusoidal Pulse Width Modulation (SPWM) and Space Vector Modulation (SVM). When the three level NPC VSI is used as an Active Power Filter (APF) to improve the power quality at the point of common coupling, as shown in
Fig. 1, the dclink capacitors are independent. A correctly controlled APF can reduce harmonics, compensate reactive power, and balance the ac source currents.
Fig. 1. Threelevel NPC active power filter.
Control of the independent dclink capacitors in multilevel APF inverters has been extensively researched and capacitor sizing due to the transient load changes has also been considered. Capacitor voltage balance is almost achieved, but with voltage ripple. This accentuates the imbalance and becomes more serious when the instantaneous power difference between the supply and the load is more significant.

PULSE WIDTH MODULATION
PWM inverters are gradually taking over other types of inverters in industrial applications. PWM techniques are characterised by constant amplitude pulses. The width of these pulses is, however, modulated to obtain inverter output voltage control and to reduce its harmonic content. The different PWM techniques are

Single Pulse Modulation

Multiple Pulse Modulation

Sinusoidal Pulse Modulation
In PWM inverters, forced commutation is essential. The three PWM techniques listed above differ from each other in the harmonic content in their respective output voltages. Thus, choice of particular PWM technique depends upon the permissible harmonic content in the inverter output voltage.
In industrial applications, PWM inverter is supplied from a diode bridge rectifier and an LC filter. The inverter topology remains the same for single phase inverter and threephase inverter. But now the devices are switched on and off several times within each half cycle to control the output voltage which has low harmonic content.
The advantages of PWM control are

The output voltage content can be obtained without any additional component.

With this type of control, lower order harmonics can be eliminated or minimized along with its output voltage control.

The filtering requirements are minimized as higher order harmonics can be filtered easily.
The main drawback of this method is that the SCRs used in this method must have very low turnon and turnoff times (invertergrade SCRs), therefore they are very expensive.


PROPOSED SINUSOIDAL PULSE WIDTH MODULATION
In this method of modulation, several pulses per half cycle are used in the case of multiplepulse modulation (MPM). In MPM, the pulse width is equal for all the pulses. But in sin M, the pulse width is a sinusoidal function of the angular position of the pulse in a cycle. For realizing sin M, a highfrequency triangular carrier is compared with a sinusoidal reference wave of the desired
frequency. The intersection of and waves
determines the switching instants and commutation of the modulated pulse. Here, is the peak value of
triangular wave and that of reference, or modulating, signal.
When sinusoidal wave has magnitude higher than the triangular wave, the comparator output is high, otherwise it is low and it is shown in Fig. 3. The comparator output is processed in a trigger pulse generator in such a manner that the output
Fig. 2. Generation of PWM pulses.
voltage wave of the inverter has a pulse width in agreement with the comparator output pulse width.
Fig. 3. Low and High comparator output.
When triangular carrier wave has its peak coincident with zero of the reference sinusoid, there are pulses per half cycle. In case zero of the triangular wave coincides with zero of the reference sinusoid, there are (N 1) pulses per half cycle.
The ratio of is called the modulation
index (MI) and it controls the harmonic content of the output voltage waveform. The magnitude of the fundamental component of output voltage is proportional to MI, but MI can never be more than unity. Thus the output voltage is controlled by varying MI.
The carrier and reference waves are mixed in a comparator in order to produce the PWM triggering pulses as shown in Fig. 2.
If is the width of the th pulse, the rms value of output voltage is obtained by the equation
. Harmonic analysis of
the output modulated voltage wave reveals that sin M has the following important features:

For MI less than one, largest harmonic amplitudes in the output voltage are associated with harmonics of order
or, where N is the
number of pulses per half cycle. Thus, by

increasing the number of pulses per half cycle, the order of dominant harmonic frequency can be raised, which can then be filtered out easily. If N=5, therefore harmonics of order 9 and 11 become significant in the output voltage. It may be noted that the highest order of significant harmonic ofa modulated voltage wave is centered on the carrier .
It is absorbed from above that as N is increased; the order of significant harmonic increases and the filtering requirements are accordingly minimized. But higher value of N entails higher switching frequency of thyristors. Thus a compromise between the filtering requirements and inverter efficiency should be made.

For MI greater than one, lower order harmonics appear, since for , pulse width is no longer a sinusoidal function of the angular position of the pulse.
The switches in the voltage source inverter can be turned on and off as required. In the simplest approach, the top switch is turned on if turned on and off only once in each cycle, a square wave waveform results. However, if turned on several times in a cycle an improved harmonic profile may be achieved.
In the most straightforward implementation, generation of the desired output voltage is achieved by comparing the desired reference waveform (modulating signal) with a highfrequency triangular
carrier wave as depicted schematically in Fig. 4. Depending on whether the signal voltage is larger or smaller than the carrier waveform, either the positive or negative dc bus voltage is applied at the output. Note that over the period of one triangle wave, the average voltage applied to the load is proportional to the amplitude of the signal (assumed constant) during this period.
The resulting chopped square waveform contains a replica of the desired waveform in its low frequency components, with the higher frequency components being at frequencies of a close to the carrier frequency. Notice that the root mean square value of the ac voltage waveform is still equal to the dc bus voltage, and hence the total harmonic distortion is not affected by the PWM process. The
harmonic components are merely shifted into the higher frequency range and are automatically filtered due to inductances in the ac system.
When the modulating signal is a sinusoid of amplitude Am, and the amplitude of the triangular carrier is Ac, the ratio m=Am/Ac is known as the modulation index. Note that controlling the modulation index therefore controls the amplitude of the applied output voltage.
Fig. 4. Principle of SPWM
With a sufficiently high carrier frequency (see Fig. 5 drawn for fc/fm = 21 and t = L/R = T/3; T = period of fundamental), the high frequency components do not propagate significantly in the ac network (or load) due the presence of the inductive elements. However, a higher carrier frequency does result in a larger number of switchings per cycle and hence in an increased power loss.
Typically switching frequencies in the 215 kHz range are considered adequate for power systems applications. Also in threephase systems it is
advisable to use so that all three waveforms are symmetric.
Fig. 5. SPWM with
Fig. 6. Over modulation m=1.3
SPWM Spectra:
Although the SPWM waveform has harmonics of several orders in the phase voltage waveform, the dominant ones other than the fundamental are of order n and nÂ±2
where . This is evident for the spectrum
for n=15 and m = 0.8 shown in Fig. 7. Note that if the other two phases are identically generated but 120o apart in phase, the lineline voltage will not have any triplen harmonics. Hence it is advisable to choose
as then the dominant harmonic
Note that the process works well for .
For , there are periods of the triangle wave in
which there is no intersection of the carrier and the signal as in Fig. 6. However, a certain amount of this over modulation is often allowed in the interest of obtaining a larger ac voltage magnitude even though the spectral content of the voltage is rendered somewhat poorer. Note that with an odd ratio for
, the waveform is antisymmetric over a 360
degree cycle. With an even number, there are harmonics of even order, but in particular also a small dc component. Hence an even number is not recommended for single phase inverters, particularly
for small ratios of .
will be eliminated.
It is evident from Fig 7. b), that the dominant 15th harmonic in Fig. 7.a) is effectively eliminated in the line voltage. Choosing a multiple of 3 is also convenient as then the same triangular waveform can be used as the carrier in all three phases, leading to some simplification in hardware.
Fig. 7. SPWM Harmonic Spectra: n=15, m=0.8
It is readily seen that as the
where E is the dc bus voltage, that the rms value of the output voltage signal is unaffected by the PWM process. This is strictly true for the phase voltage as triplen harmonic orders are cancelled in the line voltage. However, the problematic harmonics are shifted to higher orders, thereby making filtering much easier. Often, the filtering is carried out via the natural highimpedance characteristic of the load.


SIMULATION RESULTS
Two scenarios are implemented with balanced source side impedances. The balanced three phase rectified bridge with resistive load is shown in Fig. 1. The other adds a single phase rectified load to the balanced three phase rectified load in order to make an unbalanced nonlinear load.

Capacitor Voltage under Balanced Load
The simulation result of capacitor voltages in APF under balanced three phase rectified bridge with resistive load are shown in Fig. 8.

Voltage across C1

Voltage across C2

Voltage across C1 + C2

Voltage across C1, C2 and C1+C2 Fig. 8. Capacitor voltages under balanced load


Capacitor Voltage Spikes under Balanced Load
The capacitor voltage spikes in an APF under balanced three phase rectified bridge with resistive load are shown in Fig. 9.

Voltage spikes across C1

Voltage spikes across C2

Voltage spikes across C1 + C2

Voltage spikes across C1, C2 and C1+C2 Fig. 9. Capacitor voltage spikes under balanced load


THD value for Balanced Load
The THD value of line current for both balanced load without APF and balanced load with APF is shown in Fig. 10 and Fig. 11.
Fig. 10. THD value for balanced load without APF
Fig. 11. THD value for balanced load with APF

Evaluation of the Proposed Method
The accuracy of the proposed technique is a switching frequency ) dependent. The technique is evaluated only by APF current direction and capacitor voltage difference is considered (similar to symmetric modulation in [3] but when applied to APF). The relation between the maximum capacitor voltage difference under unbalanced load conditions and switching frequency is shown in Fig. 12.
As the switching frequency increases, the current values sampled at the beginning of each switching cycle better approximate the average current in the switching period. The capacitor balancing accuracy of this algorithm remains acceptable at a 2.5kHz switching frequency.
Fig. 12. Evaluation of the proposed method.


CONCLUSION
The new technique is to balance the capacitor voltages of the three level NPC – APF. The technique considers the average energy effect of each capacitor in each modulation cycle, thus giving the balanced results. The proposed scheme maintains almost constant capacitor voltage. It is to be noted that the voltage across the capacitors has been well balanced and the value of THD was found to be 6.70%. The proposed technique reduces hardware ratings, reduces capacitor voltage ripple, and attenuates the negative effects associated with voltage oscillations. This technique can also applicable for unbalanced three phase rectified bridge with resistive load.
REFERENCES

D. S. Zhou and D. G. Rouaud, Experimental comparisons of space vector neutral point balancing strategies for threelevel topology, IEEE Trans. Power Electron., vol. 16, no. 6 pp. 872879, Nov. 2001.

N. Celanovic and D.Boroyevich, A comprehensive study of neutralpoint voltage balancing problem in threelevel neutral pointclamped voltage source PWM inverters, IEEE Trans. Power Electron., vol. 15, no. 2, pp. 242249, Mar. 2000.

J. Pou, R. Pindado, D. Boroyevich, and P. Rodriguez, Evaluation of the lowfrequency neutralpoint voltage oscillations in the thee level inverter, IEEE Trans. Power Electron., vol. 52, no. 6, pp. 15821588, Dec. 2005.

S. BusquetsMonge, J. Bordonau, D. Boroyevich, and S. Somavilla, The nearest three virtual space vector PWMA comprehensive neutralpoint balancing in the threelevel NPC inverter, IEEE Power Electron. Lett., vol. 2, no. 1, pp. 1115, Mar. 2004.

J. Pou, J. Zaragoza, P. Rodriguez, S. Ceballos, V. M. Sala, R. P. Burgos, and D. Boroyevich, Fastprocessing modulation strategy for the neutral point clamped converter with total elimination of low frequency voltage oscillations in the neutral point, IEEE Trans. Ind. Electron., vol. 54, no. 4, pp. 22882294, Aug. 2007.

T. T Jin, J.Wen, and K. Smedley, Control and topologies for threephase threelevel active power filters, in Proc. Appl. Power Electron. Conf. (APEC 2005), Austin, TX, Mar. 610, pp. 655664.

B.R. Lin, C. H. Huang, T.Y. Yang, and Y.
C. Lee, Analysis and implementation of shunt active power filter with threelevel PWM scheme, in Proc. Power Electron. Drive Syst. (PEDS 2003), Singapore, Nov. 1720, pp. 15801585.

V. Aburto, M. Schneider, L. Moran, and J. Dixon, An active power filter implemented with a threelevel NPC voltagesource inverter, in IEEE Power Electron. Spec. Conf. (PESC 1997) Rec., St. Louis, MO, Jun. 22 27, pp. 11211126.

A. M. Massoud, S. J. Finney, A. J. Cruden, and B. W. Williams, Threephase, three wire, fivelevel cascaded shunt active filter for power conditioning, using two different space vector modulation techniques, IEEE Trans. Power Del., vol. 22, no. 4, pp. 2349 2361, Oct. 2007.

P. C. Tan, P. C. Loh, and D. G. Holmes, A robust multilevel hybrid compensation system for 25kV electrified railway applications, IEEE Trans. Power Elect., vol. 19, no. 4, pp. 10431052, Jul. 2004.

M. Basu, S. P. Das, and G. K. Dubey, Parallel converter scheme for highpower active power filters, in Inst. Electr. Eng. Proc. Electr. Power Appl., Jul. 2004, vol. 151, no. 4, pp. 460466.

N. Celanovic and D. Boroyevich, A fast spacevector modulation algorithm for multilevel threephase converters, IEEE Trans. Ind. Appl., vol. 37, no. 2, pp. 637 641, Mar./Apr. 2001.