 Open Access
 Total Downloads : 15
 Authors : Aravind. G. S, P. Ebby Darney
 Paper ID : IJERTCONV3IS05017
 Volume & Issue : NCETET – 2015 (Volume 3 – Issue 05)
 Published (First Online): 24042018
 ISSN (Online) : 22780181
 Publisher Name : IJERT
 License: This work is licensed under a Creative Commons Attribution 4.0 International License
Closed Loop Control of PWM Based Soft Switched Non Isolated DCDC Boost Converter
Aravind. G. S, P. Ebby Darney
PG Scholars, Associate Prof, EEE Department
SCAD College of Engineering and Technology Cheranmahadevi, Tirunelveli District, Tamilnadu,India
Abstract The conventional boost converter need high duty cycle to obtain high output voltage as well as high power. In order to obtain high voltage and power, the size and rating of the power semiconductor used should be increased. This semiconductor switch will increase conduction loss of the system and also reverse recovery problem is present. To reduce these problems nonisolated non isolated high step up DCDC converter with soft switching technique is used. But PWM based this technique has high turn off switching losses. To reduce the turn off switching losses a new method called resonant PWM (RPWM) based soft switching nonisolated high step up DCDC converter is used. The RPWM is performed by utilizing LrCr resonance in the auxiliary circuit; the capacitance is significantly reduced compared to the pulse width modulation method. Because of reduced switching losses, diode reverses recovery problems and increased step up ratio. A PWM based closed loop control is employed to this converter to enhance the load regulation and reliability of the control. The characteristics of Fuzzy Logic based closed loop control system is studied and the transient parameters are obtained. The Fuzzy Logic controller gives better performance on control the voltage under transient conduction.

INTRODUCTION
The use of nonisolated high stepup dcdc converters has been increasing with the use of renewable energy sources like photo voltage system and wind energy systems and also used for the development of dc backup energy storage. Large input current and high output voltage are the two main factors related to the efficiency of the system The large input current results from low input voltage; therefore, low voltage rated devices with low on state resistance are necessary in order to reduce the conduction loss. The boost and buckboost converters are the simplest nonisolated topologies. The nonisolated converters can provide high stepup voltage gain without incurring extreme duty ratios. A coupled inductor high stepup dcdc converter utilizes a voltage doubler and adjusts the turn ratios of the coupled inductor. This converter has been highly efficient because it recycles the energy stored in the leakage inductor of the coupled inductor, but stress across the switches is high and large inductor leakage current may damage the switches.
Most of the coupledinductor and switchedcapacitor converters are hard switched. The hardswitched CCM boost converter suffers from severe diode reverserecovery problem in highcurrent highpower applications. That is, when the main switch is turned on, a shoot through of the output capacitor to ground due to the diode reverse recovery causes a large current spike through the diode and main switch. This not only incurs significant turnoff loss of the diode and turnon loss of the main switch, but also causes severe electromagnetic interference (EMI) emission. The effect of the reverserecoveryrelated problems becomes more significant for high switching frequency at high power level. Therefore, the hardswitched CCM boost converter is not capable to achieve high efficiency and high power density at high power level. Therefore, they are not suitable for high efficiency and highpower applications.
Some softswitched interleaved high stepup converter topologies have been proposed to achieve high efficiency at desired level of volume and power level. Among them, the softswitched continuous conduction mode (CCM) boost converter demonstrated reduced voltage stresses of switches and diodes and zerovoltage switching (ZVS) turnon of the switches in CCM and zero current switching (ZCS) turnoff of the diodes. However, a drawback of this pulse width modulation (PWM) converter is high turnoff switch losses. In this project, an improved switching method, called resonant PWM (RPWM) is proposed for the softswitched CCM boost converter in order to reduce the turnoff switching losses.

OPERATING PRINCIPLES OF THE PROPOSED CONVERTER
Fig.1.Proposed ZVZCS RPWM DCDC converter.
PWM method and Resonant PWM method has same circuit topology. Main boost converter and an auxiliary circuit are the two main part of the proposed converter. The resonant capacitor Cr, resonant inductor Lr and two diodes DL and DU are the two main part of the auxiliary circuit. The two switches S1 and S2 regulated the output voltage of the system. This is a CCM mode converter. The turning of the converter is happen due to the high value of peak current. . But in the resonant PWM (RPWM) converter, the switches are turned off with resonance attained by the resonant capacitor Cr and inductor Lr of the system. The current through the resonant circuit decides which switch is turned on and off.
control to regulate the output voltage is introduced which is based on PWM based control.

MODES OF OPERATION
The operating modes and the key wave of the proposed converter are shown in figs.
Mode 1(ToT1): This mode begins when upper switch Su which was carrying the current of difference between iLf is turned OFF.SL can be turned ON with ZVS if signal for SL is applied before the current direction reversed. Filter inductor current iLf and auxiliary current iLr starts to linearly increase and decrease, respectively, as follows.
When closed loop system is introduced, response
iLf = Vi
(1)
of the system is increased and also the steady state of the
L1
system is reduced. The resonant PWM (RPWM) converter
iLr = Vc1Vc2Vc3
(2)
reduces the conduction losses of the system. It also reduced the reverse recovery problems of the switching diode. This will help to reduce the size of the system. The closed loop
L2
Fig 2 : Mode of operating of the proposed RPWM converter.
Mode 2(T1T2): In the beginning of this mode the Lr and Cr, auxiliary inductor and capacitor of the auxiliary circuit are resonant with each other. Current iLf is still linearly increasing. The voltage and current of resonant components are determined, respectively, as follows:
The resonance mode ends when iLr reaches to zero. Note that DL is turned OFF under ZCS condition.
Mode 3(T2T3): There is no current path through the auxiliary circuit during this mode. Output capacitors supply
the load. At the end of this mode the turnoff signal of SL is
iL1 = Vi
(3)
applied. It is noted that the turnoff current of SL, ISL is
L1
limited to filter inductor current at T3, ILf which is much smaller than that of PWM method.
=
=
iL2 Vc1Vc3
L2
(4)
iL1 = Vi
L1
Mode 4(T3T4): This mode begins when lower switch SL is turned OFF. SU can be turned ON with ZVS if gate signal for SU is applied before the current direction of SU is reversed. Filter inductor current iLf starts to linearly decrease since voltage vLf becomes negative.

Specifications:
Determinations of the operating requirements for the hardware design are
Pout (max):2kW Vinput range: 70V
Line frequency fL: 50 kHz
iL1 = ViVc3
(6)
Output voltage Vout: 380 VDC
L1

Selection of switching frequency (fs):
iL2 = Vc1Vc2
(7)
The switching frequency of the system must be high
L2
In this mode the other LrCr resonance of auxiliary circuit is started, and DU starts conducting as same as Mode 2. At the end of this mode the current iLr is equal to iLf .
Mode 5(T4T3): This mode begins when the currents iLr equals iLf , the direction of the upper switch iSU changes, then this mode begins. At the end of this mode, turnoff signal of SU is applied and this mode ends. The modes of operation of the system are shown in fig.2


CONTROL CIRCUIT OF PROPOSED CONVERTER.
Fig.3 Closed loop control of the proposed converter
The closed loop control of the proposed converter is as shown in fig.3. The closed loop control will help to maintain the system stability under transient condition. The closed loop control of the proposed converter is done with the help of a FUZZY Logic controller. The function of the FUZZY Logic controller is to maintain the system stability under transient conditions. This is done by comparing a part of the output voltage with a reference voltage Vref. The output of the error signal is given into a FUZZY Logic controller. The FUZZY Logic controller produce corresponding error signal and it is then given into a PWM converter. The PWM converter produces the corresponding PWM signals and is then given to gates of the switches. The switches will turned on and off with respect to the gate signal given to the system.
DESIGN OF THE PROPOSED CONVERTER
The load regulation of the converter is taken as 2kW. Although the design is developed for 2kW rating, the control circuit remains more or less the same for output ranging from 50 W to 5kW.
enough to minimize the size of power circuit and reduce distortion. On the other hand it should be less for greater efficiency. Compromising between the two factors the value is selected as 50 KHz.

Selection of resonant frequency (fr):
The resonant frequency must be designed to reduce the total switching loss of the systems. In the below resonant condition both switch turnoff current and diode di/dt are smaller. Therefore, the resonant frequency can be determined by
fr fs /2Deff
fr = 50×103/(2×0.63) = 39.68 kHz = 40 kHz

Input current.
Pinput = Pout (max)
Ipk = P/ Vinput= 2×103/70=28.571 A

Ripple current.
Ripple current is usually assumed to about 30% of the peak inductor current.
I = 0.3 x Ipk= 0.3×28.57=8.57 A peak to peak

Determination of the duty cycle of the system
Vo = (2Vin / ( 1D))Vo
Vo=5% of the output voltage D=1(2Vinput/ (Vo+Vo))
= 1(2×70/ (380+19))=0.649

To determine the effective duty ratio of the system
Vo = (2Vin / (1Deff))
Deff = 1(2 Vin / Vo)=1(2×70/380)=0.63

To determine the output current

Io=Pout/Vo= 2000/380=5.263A

To determine the input inductor
Lf=DxVin/2Iin fs=(0.64×70)/(2×8.571x50x103)
=52.27ÂµH =50ÂµH
In the practical case input inductor is chosen as 50ÂµH.

To determine the value of auxiliary resonant inductor and auxiliary resonant capacitor. Auxiliary inductor is assumed to be Lr 6ÂµH. Resonant frequency fr
=1/2LrxCr
Auxiliary capacitor Cr =1/4 2x(40×10 3)2 x6x106
=2.64×106=2.7ÂµF.

Selection of output resistor with output current value, and output voltage. R =
(Pout/ Io2) = (2000/5.2632) = 72.2

PARAMETERS FOR SIMULATION
Parameters
Design values
Input voltage
70V
Output voltage
380V
Switching frequency
50KHz
Input inductance
50ÂµH
Auxiliary capacitance
2.7ÂµF
Auxiliary resonant inductor
6ÂµH
Output current
5.45A
Power
2 kW
Output Resistance
72
Table 1 Parameters for circuit design

FUZZY LOGIC CONTROLLER DESIGN
The block diagram of fuzzy logic controller (FLC) is shown in fig.4. It consists of three main blocks: fuzzification, inference engine and defuzzification. The two FLC input variables are the error e and change in error e*. Depending on membership functions and the rules FLC operates.
Fig 4:Block Diagram of Fuzzy logic controller

Fuzzification
The membership function values are assigned to the linguistic variables using seventeen fuzzy subsets. Table2 shows the rules of FLC. E and E* are input variables, where E is the error between the reference and actual voltage of the system, E* is the change in error in the sampling interval.
E*
E
NE
ZE
PE
NE
NE
NE
NE
ZE
NE
ZE
PE
PE
PE
PE
PE
TABLE 2: RULE TABLE FOR FLC

Inference Engine
Mamdani method is used with MaxMin operation fuzzy combination. Fuzzy inference is based on fuzzy rules. Rules are framed in inference engine block. The output membership function of each rule is given by MIN (Minimum) operator and MAX (Maximum) operator.

Defuzzification

The output of fuzzy controller is a fuzzy subset. As the actual system requires a non fuzzy value of Control, defuzzication is required. Defuzzifier is used to convert the linguistic fuzzy sets back into actual value
Fig:5 Membership Functions of Error (e)
Fig:6 Membership Functions of Change in Error(e*)
Fig:7: Membership Function of Duty Cycle


SIMULATION RESULTS
The simulation result of the system is as shown below.
Fig:8 Output voltage wave form of the existing system
Fig:8 Output current wave form of the existing system

CONCUSION
A DCDC converter for high step up and high power applications is proposed. From the simulation results it is observed that ZVS turn on and ZCS turn off of all the switches is obtained. The voltage stress across the switches is much lesser. The Capacitor size and inductor size are reduced in the proposed topology by adapting proper switching scheme. The output voltage ripple can be reduced to 5%. The closed loop control adjusted the duty ratio of the system. The closed loop control limits the output voltage disturbances in particular limits.
.
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